Electric circuit

ABSTRACT

A transistor has variation in a threshold voltage or mobility due to accumulation of factors such as variation in a gate insulating film which is caused by a difference of a manufacturing process or a substrate to be used and variation in a crystal state of a channel formation region. The present invention provides an electric circuit which is arranged such that both electrodes of a capacitance device can hold a voltage between the gate and the source of a specific transistor. Further, the present invention provides an electric circuit which has a function capable of setting a potential difference between both electrodes of a capacitance device so as to be a threshold voltage of a specific transistor.

TECHNICAL FIELD

The present invention relates to the art of electric circuits.Specifically, it relates to the art of electric circuits havingtransistors.

BACKGROUND

The integrated circuit (IC), for broad use recently on a cellular phoneor personal digital assistant, is formed with transistors or resistorsas many as several hundreds of thousands to several millions on asilicon substrate in a size of nearly a 5-mm square. This plays animportant role in device miniaturization and reliability improvement,and device mass production.

In designing an electric circuit for use on an integrated circuit (IC)or the like, it is frequent cases to design an amplifier circuit havinga function to amplify a voltage or current of a signal small inamplitude. The amplifier circuit is broadly used because of a circuitrequisite for eliminating strain occurrence to stably operate anelectric circuit.

SUMMARY

The present invention has been made in view of the above problems. It isa problem to provide an electric circuit suppressing against theaffection of transistor characteristic variation. More specifically, itis a problem, in an electric circuit having a function of currentamplification, to provide an electric circuit capable of supplying adesired voltage while suppressing against the affection of thresholdvoltage variation of a transistor.

Means for Solving the Problems

In order to solve the above-mentioned problems, the present inventionuses an electric circuit with a structure described below.

The details of one or more embodiments of the invention are set forth inthe accompanying drawings and the description below. Other features,objects, and advantages of the invention will be apparent from thedescription and drawings, and from the claims.

DESCRIPTION OF DRAWINGS

FIGS. 1A and 1B are diagrams illustrating operations of a sourcefollower circuit of the present invention.

FIGS. 2A and 2B are diagrams illustrating operations of a sourcefollower circuit of the present invention.

FIGS. 3A-3E are diagrams illustrating a structure and operations of anelectric circuit of the present invention.

FIGS. 4A-4C are diagrams illustrating the principle of electric chargepreservation.

FIGS. 5A-5C are diagrams illustrating operations of a source followercircuit.

FIGS. 6A and 6B are diagrams illustrating operations of a sourcefollower circuit.

FIGS. 7A-7C are diagrams illustrating operations of a source followercircuit of the present invention.

FIG. 8 is a diagram illustrating a structure of a differential amplifiercircuit of the present invention.

FIG. 9 is a diagram illustrating a structure of a differential amplifiercircuit of the present invention.

FIGS. 10A and 10B are diagrams illustrating a structure of anoperational amplifier of the present invention.

FIGS. 11A-11C are diagrams showing a semiconductor device of the presentinvention.

FIG. 12 is a diagram showing pixels and a circuit for bias of thesemiconductor device of the present invention.

FIGS. 13A and 13B are diagrams illustrating a structure of an electriccircuit of the present invention.

FIG. 14 is a diagram of a signal line drive circuit of the presentinvention.

FIG. 15 is a diagram of the signal line drive circuit of the presentinvention.

FIG. 16 is a diagram illustrating operations of the signal line drivecircuit of the present invention.

FIG. 17 is a diagram showing an operational amplifier of the presentinvention.

FIG. 18 is a diagram showing the operational amplifier of the presentinvention.

FIG. 19 is a diagram showing the operational amplifier of the presentinvention.

FIGS. 20A-20H are illustrations of electric appliances to which thepresent invention is applied.

FIGS. 21A and 21B are diagrams illustrating a structure of anoperational amplifier of the present invention.

FIG. 22 is a diagram showing an operational amplifier of the presentinvention.

FIG. 23 is a diagram showing an operational amplifier of the presentinvention.

Like reference symbols in the various drawings indicate like elements.

DETAILED DESCRIPTION

Herein, explained is the configuration and operation of a sourcefollower circuit, as one example of amplifier circuit. At first, aconfiguration example of source follower circuit will be shown in FIG.5A to explain an operation in a steady state. Next, an operating pointof the source follower circuit will be explained, by using FIGS. 5B and5C. Finally, an example of source follower circuit different inconfiguration from FIG. 5A will be shown in FIGS. 6A and 6B, to explainan operation in a transient state.

At first, a steady state operation is explained by using a sourcefollower circuit in FIG. 5A.

In FIG. 5A, 11 is an n-channel amplifier transistor while 12 is ann-channel bias transistor. Note that, although the amplifier transistor11 and bias transistor 12 in FIG. 5A is of an n-channel type,configuration may be by the use of p-channel transistors. Herein, theamplifier transistor 11 and the bias transistor 12 are assumably thesame in characteristic and size, for simplification sake. It is furtherassumed that the current characteristic of them is ideal. Namely, it issupposed that, even if the amplifier transistor 11 or bias transistor 12is changed in its source-to-drain voltage, there is no change insaturation-region current value.

Meanwhile, the amplifier transistor 11 has a drain region connected to apower line 13 and a source region connected to a drain region of thebias transistor 12. The bias transistor 12 has a source region connectedto a power line 14.

The gate electrode of the bias transistor 12 is applied by a biaspotential V_(b). A power-source potential V_(dd) is applied onto thepower line 13 while a ground potential V_(ss) (=0V) is applied onto thepower line 14.

In the source follower circuit of FIG. 5A, the gate electrode of theamplifier transistor 11 is made as an input terminal so that an inputvoltage V_(in) can be inputted to the gate electrode of the amplifiertransistor 11. Also, the source region of the amplifier transistor 11 ismade as an output terminal so that the potential on the source region ofthe amplifier transistor 11 provides an output potential V_(out). Thegate electrode of the bias transistor 12 is applied by a bias voltageV_(b). When the bias transistor 12 operates in a saturation region, acurrent denoted by Ib assumably flows. At this time, because theamplifier transistor 11 and the bias transistor 12 are in a seriesconnection, the same amount of current flows through the bothtransistors. Namely, when a current Ib flows through the bias transistor12, a current Ib flows also through the amplifier transistor 11.

Herein, determined is an output potential V_(out) in the source followercircuit. The output potential V_(out) is lower in value than the inputvoltage V_(in), by an amount of the voltage between the gate and thesource V_(gs1) of the amplifier transistor 11. At this time, the inputvoltage V_(in), the output potential V_(out) and the voltage between thegate and the source V_(gs1) have a relationship satisfying the followingEquation (1).

[Equation 1]V _(out) =V _(in) −V _(gs1)  (1)

In the case the amplifier transistor 11 is operating in the saturationregion, in order to flow a current Ib through the amplifier transistor11 there is a necessity that the voltage between the gate and the sourceV_(gs1) of the amplifier transistor 11 is equal to a bias potentialV_(b). If so, the following Equation (2) is held. However, Equation (2)is held only when the amplifier transistor 11 and the bias transistor 12operate in the saturation region.

[Equation 2]V _(out) =V _(in) −V _(b)  (2)

Next explained is an operating point of the source follower circuit byusing FIGS. 5B and 5C showing a relationship of between a voltage and acurrent of the amplifier transistor 11 and bias transistor 12. Morespecifically, explanation is made on a case that the voltage between thegate and the source V_(gs1) of the amplifier transistor 11 is same invalue as the voltage between the gate and the source V_(gs2) of the biastransistor 12, by using FIG. 5B. Next explained is a case that thevoltage between the gate and the source V_(gs1) of the amplifiertransistor 11 is different in value from the voltage between the gateand the source V_(gs2) of the bias transistor 12 wherein, for example,the bias transistor 12 is operating in a linear region, by using FIG.5C.

In FIG. 5B, the dotted line 21 shows a relationship between a voltageand a current when the amplifier transistor 11 has a voltage between thegate and the source V_(gs1) of V_(b). The solid line 22 shows arelationship between a voltage and a current when the bias transistor 12has a voltage between the gate and the source V_(gs2) of V_(b).Meanwhile, in FIG. 5C, the dotted line 21 shows a relationship between avoltage and a current when the amplifier transistor 11 has a voltagebetween the gate and the source V_(gs1) of V_(b)′. The solid line 22shows a relationship between a voltage and a current when the biastransistor 12 has a voltage between the gate and the source V_(gs2) ofV_(b).

In FIG. 5B, the voltage between the gate and the source V_(gs1) of theamplifier transistor 11 and the voltage between the gate and the sourceV_(gs2) of the bias transistor 12 are in the same value, and further thebias potential V_(b) and the voltage between the gate and the sourceV_(gs2) of bias transistor 12 are in the same value. Consequently, thevoltage between the gate and the source V_(gs1) of the amplifiertransistor 11 is in the same value as the bias potential V_(b). Namely,this results in V_(gs1)=V_(gs2)=V_(b). The amplifier transistor 11 andthe bias transistor 12 are operating in the saturation region, as shownin FIG. 5B. At this time, the input voltage V_(in) and the outputpotential V_(out) have a relationship in a linear form.

On the other hand, in FIG. 5C, the voltage between the gate and thesource V_(gs1) of the amplifier transistor 11 is in a value differentfrom the voltage between the gate and the source V_(gs2) of biastransistor 12. Furthermore, the voltage between the gate and the sourceV_(gs2) of bias transistor 12 is in a same value as the bias voltageV_(b). Meanwhile, it is assumed that the voltage between the gate andthe source V_(gs1) of the amplifier transistor 11 is at the bias voltageV_(b)′. Namely, this results in V_(gs2)=V_(b) and V_(gs1)=V_(b)′. Asshown n FIG. 5C, the amplifier transistor 11 is operating in thesaturation region while the bias transistor 22 is operating in thelinear region. At this time, the input voltage V_(in), the outputpotential V_(out) and the bias potential V_(b)′ have a relationshipsatisfying the following Equation (3).

[Equation 3]V _(out) =V _(in) −V _(b)′  (3)

Provided that the current flowing upon operating of the bias transistor12 in the linear region is taken Ib′, Ib′<Ib is given. Namely, by havingV_(b)′<V_(b), the both values of the input voltage V_(in) and currentIb′ decrease. Thereupon, the bias potential V_(b)′ also decreases. Atthis time, the input voltage V_(in) and the output potential V_(out)have a non-linear relationship.

Summarizing the above, in order to increase the amplitude of the outputpotential V_(out) in the source follower circuit in a steady state, itis preferred to decrease the bias potential V_(b). This is because ofthe following two reasons.

The first reason is that the output potential V_(out) can be increasedat a small bias potential V_(b), as shown in Equation (2). The secondreason is that, in the case of a great bias potential V_(b) value, thebias transistor 12 readily operate in the linear region at a decreasedinput voltage V_(in). In case the bias transistor 12 operates in thelinear region, the input voltage V_(in) and the output potential V_(out)are ready to have a non-linear relationship.

Incidentally, because the bias transistor 12 is required in a conductionstate, there is a need to provide a greater value of bias potentialV_(b) than a threshold voltage of the bias transistor 12.

So far explained was the operation in a steady state of the sourcefollower circuit. Subsequently, explanation is made on the operation ofthe source follower circuit in a transient state, by using FIGS. 6A and6B.

The source follower circuit shown in FIGS. 6A and 6B has a configurationdesigned by adding a capacitance device 15 to the circuit of FIG. 5A.The capacitance device 15 has one terminal connected to the sourceregion of the amplifier transistor 11 and the other terminal connectedto the power line 16. A ground potential V_(ss) is applied onto thepower line 16.

The capacitance device 15 has a same potential difference at between itsboth electrodes as the output potential V_(out) of the source followercircuit. Herein, explained is the operation in a case ofV_(out)<V_(in)−V_(b), by using FIG. 6A. Next explained is the operationin a case of V_(out)>V_(in)−V_(b), by using FIG. 6B.

At first, explanation is made on the operation in a transient state ofthe source follower circuit in the case of V_(out)<V_(in)−V_(b), byusing FIG. 6A.

In FIG. 6A, when t=0, the voltage between the gate and the sourceV_(gs1) of the amplifier transistor 11 has a greater value than thevoltage between the gate and the source V_(gs2) of the bias transistor12. Consequently, a great current flows through the amplifier transistor11 to promptly hold charge on the capacitance device 15. Thereupon, theoutput potential V_(out) increases to decrease the voltage between thegate and the source V_(gs1) value of the amplifier transistor 11.

As time elapses (t=t1, t1>0), the amplifier transistor 11 goes into asteady state when its voltage between the gate and the source V_(gs1)becomes equal to the bias potential V_(b). At this time, the outputpotential V_(out), the input voltage V_(in) and the bias potential V_(b)have a relationship satisfying the foregoing Equation (2).

Summarizing the above, in the case of V_(out)<V_(in)−V_(b), the voltagebetween the gate and the source V_(gs1) of the amplifier transistor 11is greater in value than the bias potential V_(b). Accordingly, a greatcurrent flows through the amplifier transistor 11, to promptly holdcharge on the capacitance device 15. Hence, the time may be short thatis required for the capacitance device 15 to hold predetermined charge,in other words the time required in writing a signal to the capacitancedevice 15.

Next, explanation is made on the operation in a transient state of thesource follower circuit in the case of V_(out)>V_(in)−V_(b), by usingFIG. 6B.

In FIG. 6B, when t=0, the voltage between the gate and the sourceV_(gs1) of the amplifier transistor 11 has a smaller value than thethreshold voltage of the amplifier transistor 11. Consequently, theamplifier transistor 11 is in a non-conduction state. The charge storedon the capacitance device 15 flows in a direction toward the groundpotential V_(ss) through the bias transistor 12, finally beingdischarged. At this time, because the voltage between the gate and thesource V_(gs2) of the bias transistor 12 is in the same value as thebias potential V_(b), the current flowing through the bias transistor 12is Ib.

As time elapses (t=t1, t1>0), the output potential V_(out) decreaseswhile the voltage between the gate and the source V_(gs1) of theamplifier transistor 11 increases. When the voltage between the gate andthe source V_(gs1) of the amplifier transistor 11 becomes equal to thebias potential V_(b), a steady state is entered. At this time, theoutput potential V_(out), the input voltage V_(in) and the biaspotential V_(b) have a relationship satisfying the foregoing Equation(2). Note that, in the steady state, the output potential V_(out) iskept at a constant value, and charge does not flow to the capacitancedevice 15. Thus, a current Ib flows through the amplifier transistor 11and bias transistor 12.

Summarizing the above, in the case of V_(out)>V_(in)−V_(b), the time forthe capacitance device 15 to hold predetermined charge, in other wordsthe write time of a signal to the capacitance device 15, relies upon thecurrent Ib flowing through the bias transistor 12. The current Ib reliesupon a magnitude of the bias potential V_(b). Accordingly, in order toincrease the current Ib and shorten the write time of a signal to thecapacitance element 15, a necessity is raised to increase the biaspotential V_(b).

Incidentally, as a method of correcting for threshold-voltage variationof transistors, there is a method that variation is observed by anoutput of a circuit a signal has been inputted and thereafter thevariation is inputted and fed back thereby carrying out a correction(e.g. see Non-Patent Document 1).

[Non-Patent Document] H. Sekine et al, “Amplifier Compensation Methodfor a Poly-Si TFT LCLV with an Integrated Data-Driver”, IDRC' 97, p.45-48.

Problems to be Resolved by the Invention

The foregoing operation of the source follower circuit is to be carriedout on an assumption the amplifier transistor 11 and the bias transistor12 have the same characteristic. However, for the both transistors,variation occurs in the threshold voltage or mobility due to gatheringof the factors, such as gate insulating film thickness or variation inchannel-region crystal state caused due to the difference in fabricationprocess or substrate used.

For example, it is assumed, in FIG. 5A, that there is variation of 1 Vprovided that the amplifier transistor 11 has a threshold of 3 V and thebias transistor 12 has a threshold of 4 V. If so, in order to flow acurrent Ib, there is a need to apply a voltage for the voltage betweenthe gate and the source V_(gs1) of the amplifier transistor 11 lower by1 V than the voltage between the gate and the source V_(gs2) of the biastransistor 12. Namely, V_(gs1)=V_(b)−1 results. If so,V_(out)=V_(in)−V_(gs1)=V_(in)−V_(b)+1 results. Namely, in case variationoccurs even by 1 V in the threshold voltage of the amplifier transistor11 and bias transistor 12, variation is also caused in the outputpotential V_(out).

An electric circuit shown in FIG. 3A includes switching elements 31 and32 (hereinafter referred to as sw 31 and sw 32) having a switchingfunction, an n-channel type transistor 33, and a capacitance device 34.A source region of the transistor 33 is connected to a power supply line36 and a drain region thereof is connected to a power supply line 35 viathe sw 31. A gate electrode of the transistor 33 is connected to oneterminal of the capacitance device 34. In addition, the other terminalof the capacitance device 34 is connected to a power supply line 37. Thecapacitance device 34 carries out a function of holding a voltagebetween the gate and the source V_(gs) of the transistor 33. Inaddition, a power supply voltage V_(dd) is applied to the power supplyline 35 and a ground voltage V_(ss) is applied to the power supply lines36 and 37.

Although the transistor 33 is assumed to be an n-channel type in FIGS.3A to 3C, the transistor 33 is not limited to this and it is possible toconstitute it by a p-channel type transistor. In addition, an electriccircuit having the same circuit element as FIG. 3A and a differentconnection structure is shown in FIG. 3C. Since operations of theelectric circuit shown in FIG. 3C follow operations of the circuit shownin FIG. 3A discussed below, a description of the operations will beomitted here.

Further, in the electric circuit shown in FIG. 3A, an electric charge isheld in the capacitance device 34 such that a potential differencebetween both the electrodes of the capacitance device 34 takes the samevalue as a threshold voltage of the transistor 33. This operation willbe hereinafter described.

In FIG. 3A, the sw 31 and the sw 32 are ON. In this state, since thepower supply voltage V_(dd) is applied to the power line 35 and theground voltage V_(ss) is applied to the power supply lines 36 and 37, apotential difference is generated between the power supply line 35 andthe power supply lines 36 and 37. As a result, an electric currentI_(ds) flows from the power supply line 35 toward directions of thetransistor 33 and the capacitance device 34 via the sw 31 and the sw 32.At this point, the electric current I_(ds) branches to I₁ and I₂ andflows. Note that the electric current I_(ds) satisfies I_(ds)=I₁+I₂.

At an instance when an electric current starts flowing from the powersupply line 35 in the directions of the power supply line 36 and thepower supply line 37, an electric charge is not held in the capacitancedevice 34. Thus, the transistor 33 is OFF. Therefore, I₁=0 andI_(ds)=I₂.

Then, an electric charge is gradually stored in the capacitance device34, and a potential difference starts to be generated between both theelectrodes of the capacitance device 34. When the potential differencebetween both the electrodes has reached V_(th), the transistor 33 isturned ON, and I₁>0. Since Ids=I₁+I₂ as described above, I₂ graduallydecreases but an electric current is still flowing.

Then, in the capacitance device 34, the storage of electric charges iscontinued until the potential difference between both the electrodes ofthe capacitance device 34 reaches V_(dd). When the storage of electriccharges ends in the capacitance device 34 (FIGS. 3D and 3E, A point),the electric current I₂ stops flowing, and since the transistor 33 isON, I_(ds)=I₁.

Subsequently, as shown in FIG. 3B, the sw 31 is turned OFF. The sw 32continues to be ON. Then, the electric charges held in the capacitancedevice 34 flow in the direction of the transistor 33 via the sw 32. Morespecifically, the electric charges held in the capacitance device 34flow from the drain region of the transistor 33 in the direction of thepower supply line 36 via the source region and discharge. This operationis performed until the transistor 33 is turned OFF. That is, it iscontinued until the electric charges held in the capacitance device 34reaches the same value as the threshold voltage of the transistor 33(FIGS. 3D and 3E, B point).

In this way, electric charges are held such that a potential differencebetween both the electrodes of the capacitance device 34 takes the samevalue as the threshold voltage of the transistor 33.

As described above, the present invention provides an electric circuitwhich is arranged such that both electrodes of a capacitance device canhold a voltage between the gate and the source of a specific transistor.Further, the present invention provides an electric circuit which has afunction capable of setting a potential difference between bothelectrodes of a capacitance device so as to be a threshold voltage of aspecific transistor.

Moreover, in the present invention, a voltage between the gate and thesource of a specific transistor held in a capacitance device ispreserved as it is, and a signal voltage (voltage of a video signal,etc.) is inputted to a gate electrode of the transistor. Then, a voltagewith the signal voltage added to the voltage between the gate and thesource preserved in the capacitance device is inputted to the gateelectrode of the transistor. As a result, a value found by adding athreshold voltage of the transistor and the signal voltage is inputtedto the gate electrode of the transistor. That is, in the presentinvention, even if threshold voltages fluctuate among transistors, thevalue found by adding the threshold value of the transistor and thesignal voltage is always inputted to a transistor to which a signalvoltage is inputted. Thus, an electric circuit can be provided in whichan influence of the variation of threshold values among transistors issuppressed.

Note that the mechanism in which a signal voltage is added to a voltagebetween the gate and the source held in a capacitance device can beexplained according to the principle of electric charge preservation.The principle of electric charge preservation indicates the fact that atotal quantity of electricity of an algebraic sum of a quantity ofpositive electricity and a quantity of negative electricity is definite.Here, the principle of electric charge preservation will be describedusing FIGS. 4A to 4C.

In FIGS. 4A to 4C, reference numeral 26 denotes a power supply(constant-voltage source) and 27 denotes a capacitance device. The powersupply 26 and the capacitance device 27 are connected via an sw 28. Thepower supply 26 is connected to a power supply line 29 and thecapacitance device 27 is connected to a power supply line 30.

In FIG. 4A, the sw 28 is ON, and 0 V is applied to the power supply line29 and the power supply line 30. Further, a voltage V_(x) is applied tothe power supply 26, and the sw 28 is in a conduction state in thisstate. As a result, electric charges are held in the capacitance device27 such that a potential difference between both electrodes of thecapacitance device 27 becomes V_(x).

Subsequently, in FIG. 4B, the sw 28 is turned OFF. At this point, theelectric charges held in the capacitance device 27 continue to be heldaccording to the principle of electric charge preservation.

Then, in FIG. 4C, a voltage V_(y) is applied to the power supply line 30connected to one terminal of the capacitance device 27. The sw 28 is OFFand 0 V is applied to the power supply line 29. At this point, theelectric charges held in the capacitance device 27 are preserved, and avoltage V_(y) to be applied to the power supply line 30 is added to theelectric charges. That is, as shown in FIG. 4C, a voltage of oneterminal of the capacitance device 27 becomes (V_(y)+V_(x)).

In this way, in the capacitance device 27, when the held electriccharges continue to be preserved as they are and a voltage of oneterminal of the capacitance device 27 increases, a voltage of the otherterminal increases accordingly.

Note that, in the present invention, a transistor using any material anda transistor undergone any means and manufacturing method may be used,and a transistor of any type may be used. For example, a thin filmtransistor (TFT) may be used. As the TFT, a TFT with any of anamorphous, polycrystal, and single crystal semiconductor layers may beused. As other transistors, a transistor produced on a single crystalsubstrate or a transistor produced on an SOI substrate may be used. Inaddition, a transistor formed of an organic matter or a carbon nanotubemay be used. Moreover, an MOS transistor or a bipolar transistor may beused.

Mode for Carrying Out the Invention

(Embodiment 1)

In this embodiment, a source follower circuit will be indicated as anexample of the electric circuit of the present invention, and astructure and operations thereof will be described using FIGS. 1 and 2.

In FIGS. 1 and 2, reference numeral 211 denotes an n-channel typetransistor for amplification and 212 denotes an n-channel typetransistor for bias. Reference numerals 213 and 214 denote capacitancedevices. In addition, reference numerals 215 to 222 denote elementshaving a switching function, and preferably, a semiconductor elementsuch as a transistor or an analog switch is used. Reference numerals 223and 224 denote power supply lines, and a power supply voltage V_(dd) isapplied to the power supply line 223 and a ground voltage V_(ss) isapplied to the power supply line 224.

Note that, in this embodiment, although a case in which the transistorfor amplification 211 and the transistor for bias 212 are the n-channeltype is shown, the present invention is not limited to this and both thetransistors may be the p-channel type. In addition, polarities of boththe transistors may be different.

In the case in which polarities of both the transistors are different,since a push-pull circuit is constituted, both the transistors functionas the transistor for amplification. Thus, signals are inputted to boththe transistors.

A drain region of the transistor for amplification 211 is connected tothe power supply line 223 and a source region thereof is connected tothe switches 217 to 219. A gate electrode of the transistor foramplification 211 is connected to one terminal of the capacitance device213. The other terminal of the capacitance device 213 is connected tothe source region of the transistor 211 via the switch 217. Thecapacitance device 213 carries out a function of holding a voltagebetween the gate and the source (threshold voltage) of the transistorfor amplification 211. Note that the transistor for amplification 211will hereinafter represented as the transistor 211.

A source region of the transistor for bias 212 is connected to the powersupply line 224 and a drain region thereof is connected to the switches219 and 220. A gate electrode of the transistor for bias 212 isconnected to one terminal of the capacitance device 214. The otherterminal of the capacitance device 214 is connected to the source regionof the transistor for bias 212 via the switch 222. The capacitancedevice 214 carries out a function of holding a voltage between the gateand the source (threshold voltage) of the transistor for bias 212. Notethat the transistor for bias 212 will be hereinafter represented as thetransistor 212.

Conduction or non-conduction (ON or OFF) of the switches 215 to 222 iscontrolled according to a signal to be inputted. However, in FIGS. 1 and2, illustration of a signal line or the like for inputting a signal tothe switches 215 to 222 is omitted in order to simplify explanation.

In the source follower circuit shown in FIGS. 1 and 2, one terminal ofthe switch 216 becomes an input terminal. Via the input terminal, aninput voltage V_(in) (signal voltage) is inputted to the gate electrodeof the transistor 211 via the switch 216 and the capacitance device 213.In addition, a bias voltage V_(b) is inputted from one terminal of theswitch 221. The bias voltage V_(b) is inputted to a gate electrode ofthe transistor 212 via the switch 221 and the capacitance device 214. Inaddition, one terminal of the switch 218 is an output terminal, and avoltage of the source region of the transistor 211 becomes an outputvoltage V_(out).

Note that, although the switch 218 is connected to the source region ofthe transistor 211 and connected to the drain region of the transistor212 via the switch 219, the present invention is not limited to this.The switch 218 may be connected to the drain region of the transistor212 and connected to the source region of the transistor 211 via theswitch 219.

However, the switch 218 is preferably connected to the source region ofthe transistor 211 and connected to the drain region of the transistor212 via the switch 219. This is because, in the case in which the switch218 is connected to the drain region of the transistor 212 and connectedto the source region of the transistor 211 via the switch 219, if thereis an ON resistance in the switch 219, the output voltage V_(out) isaffected by it and decreases.

Next, operations of the source follower circuit shown in FIGS. 1 and 2will be described.

In FIG. 1A, the switch 215, the switch 217, the switch 219, the switch220, and the switch 222 are turned ON. Further, the other switches areturned OFF. In this state, since V_(dd) is applied to the power supplyline 223 and V_(ss) is applied to the power supply line 224, a potentialdifference is generated between the power supply line 223 and the powersupply line 224. As a result, an electric current flows toward thedirection of the power supply line 224 from the power supply line 223.

At an instance when an electric current starts flowing in the directionof the power supply line 224 from the power supply line 223, electriccharges are not held in the capacitance device 213 and the capacitancedevice 214. Therefore, the transistor 211 and the transistor 212 areOFF. The electric current flows in the direction of the power supplyline 224 from the power supply line 223 via the switch 215 and theswitch 217, subsequently via the switch 219, and further via the switch220 and the switch 222.

Then, electric charges are gradually stored in the capacitance devices213 and 214, and a potential difference starts to be generated betweenboth the electrodes of the capacitance devices 213 and 214. When thepotential difference between both the electrodes of the capacitancedevice 213 reaches a threshold voltage V_(th1) of the transistor 211,the transistor 211 is turned ON. Similarly, when the potentialdifference between both the electrodes of the capacitance device 214reaches a threshold voltage V_(th2) of the transistor 212, thetransistor 212 is turned ON.

In the capacitance devices 213 and 214, storage of electric charges iscontinued until the elements come into a stationary state.

Subsequently, as shown in FIG. 1B, when the storage of electric chargesends in the capacitance devices 213 and 214 and the elements comes intothe stationary state, the switch 219 is turned OFF from ON, and theother switches maintain the state of FIG. 1A.

Then, positive electric charges held in the capacitance device 213 flowin the direction of the transistor 211 via the switch 215. Morespecifically, the positive electric charges held in the capacitancedevice 213 flow from the drain region of the transistor 211 via theswitch 215 in the direction of the capacitance device 213 via the sourceregion thereof and further via the switch 217. As a result, thepotential difference between both the electrodes of the capacitancedevice 213 decreases. This operation is performed until the transistor211 is turned OFF. That is, it is continued until the electric chargesheld in the capacitance device 213 become the same value as thethreshold voltage V_(th1) of the transistor 211.

In addition, positive electric charges held in the capacitance device214 flow in the direction of the transistor 212 via the switch 220. Morespecifically, the positive electric charges held in the capacitancedevice 214 flow from the drain region of the transistor 212 via theswitch 220 in the direction of the power supply line 224 via its sourceregion. This operation is performed until the transistor 212 is turnedOFF. That is, it is continued until the electric charges held in thecapacitance device 214 become the same value as the threshold voltageV_(th2) of the transistor 212.

In this way, the potential difference between both the electrodes of thecapacitance device 213 takes the same value as the threshold voltageV_(th1) of the transistor 211. In addition, the potential differencebetween both the electrodes of the capacitance device 214 takes the samevalue as the threshold voltage V_(th2) of the transistor 212.

When the potential difference between both the electrodes of thecapacitance device 213 takes the same value as the threshold voltageV_(th1) of the transistor 211 and the potential difference between boththe electrodes of the capacitance device 214 takes the same value as thethreshold voltage V_(th2) of the transistor 212 as described above, theswitch 215, the switch 217, the switch 220, and the switch 222 areturned OFF (FIG. 2A). That is, at this point, all the switches 215 to222 are OFF.

Note that it is desirable to turn off the switch 215, the switch 217,the switch 220, and the switch 222 after the potential difference ofboth the electrodes of the capacitance devices 213 and 214 take the samevalues as the threshold voltages V_(th1) and V_(th2) of the transistors211 and 212. However, the present invention is not limited to this. Inthe case in which variation of the transistors 211 and 212 is small,since operations of the electric circuit does not specifically cause aproblem, the switch 215, the switch 217, the switch 220, and the switch222 may be turned OFF when the potential differences between both theelectrodes of the capacitance devices 213 and 214 take values close tothe threshold voltages V_(th1) and V_(th2) of the transistors 211 and212, and timing therefore is not specifically limited.

Subsequently, the switch 216, the switch 218, the switch 219, and theswitch 221 are turned ON (FIG. 2B). The other switches keep to be OFF.At this point, an input voltage V_(in) is applied to the gate electrodeof the transistor 211 from the input terminal via the switch 216 and thecapacitance device 213. At this point, according to the principle ofelectric charge preservation, a value found by adding the input voltageV_(in) to the threshold voltage V_(th1) of the transistor 211(V_(th1)+V_(in)) is applied to the gate electrode of the transistor 211.In addition, a value found by adding the input voltage V_(b) to thethreshold voltage V_(th2) of the transistor 212 (V_(th2)+V_(b)) isapplied to the gate electrode of the transistor 212.

Note that, when a transistor operates in a saturation region, expression(4) shown below is established. I_(ds) is an amount of electric currentflowing in a channel formation region of the transistor and V_(gs) is avoltage between the gate and the source of the transistor. In addition,V_(th) is a threshold voltage of the transistor.

[Numeral 4]I_(ds)∝(V_(gs)−V_(th))²  (4)

In the above expression (4), when it is assumed V_(k)=V_(gs)−V_(th),expression (5) shown below is established.

[Numeral 5]I_(ds)∝V_(k) ²  (5)

From expression (5), it is seen that I_(ds) is proportional to a squareof V_(k) which is a value found by deducting a value of V_(th) fromV_(gs).

Here, the above expressions (4) (5) are applied to the transistors 211and 212 to find an output voltage V_(out). Note that, in thisembodiment, it is assumed that gate widths (W) and gate lengths (L) ofthe transistors 211 and 212 do not fluctuate but are identical. On theother hand, it is assumed that the threshold voltages V_(th1), V_(th2)of the transistors 211 and 212 fluctuate.

When a voltage applied to the gate electrode of the transistor 212 isassumed to be V_(a2), V_(a2)=V_(b)+V_(th2) is established. Moreover,when a value found by deducting the threshold voltage V_(th2) from thevoltage V_(a2) applied to the gate electrode of the transistor 212 isassumed to be V_(k2), expression (6) shown below is established.

[Numeral 6]V _(k2) =V _(a2) −V _(th2)=(V _(b) +V _(th2))−V _(th2) =V _(b)  (6)

Then, when a voltage applied to the gate electrode of the transistor 211is assumed to be V_(a1), expression (7) shown below is established.

[Numeral 7]V _(a1) =V _(in) +V _(th1)  (7)

Moreover, when a value found by deducting the threshold voltage V_(th1)from the voltage between the gate and the source V_(gs1) of thetransistor 211 is assumed to be V_(k1), expression (8) shown below isestablished.

[Numeral 8]V _(k1) =V _(gs1) −V _(th1)  (8)

Here, since the same amount of electric current flows to the transistors211 and 212, expression (9) shown below is established.

[Numeral 9]V_(k1)=V_(k2)=V_(b)  (9)

Further, since the output voltage V_(out) is a voltage of the sourceregion of the transistor 211, expression (10) shown below isestablished.

[Numeral 10]V _(out) =V _(a1) −V _(gs1)=(V _(in) +V _(th1))−(V _(b) +V _(th1))=V_(in) −V _(b)  (10)

As indicated in expression (10), the output voltage V_(out) takes avalue found by deducting the bias voltage V_(b) from the input voltageV_(in) and does not depend upon the threshold voltage. Thus, even if thethreshold voltages of the transistor 211 and 212 fluctuate, an influenceexerted on the output voltage V_(out) can be suppressed.

Note that, although it is assumed in this embodiment that the gatewidths (W) and the gate lengths (L) of the transistors 211 and 212 donot fluctuate but are identical, sizes of the gate widths (W) and thegate lengths (L) of both the transistors are not specifically limited.

In addition, in FIG. 7C, a source follower circuit in the case in whichthe transistor for bias 212 is not arranged is shown. Since operationsof the source follower circuit shown in FIG. 7C are the same as theoperations in FIGS. 1 and 2 described above except that the switch 219is turned OFF at the time of the output operation, a description of theoperations will be omitted in this embodiment.

Note that, in this specification, an operation for holding predeterminedelectric charges in a capacitance device is referred to as a settingoperation. In this embodiment, the operations of FIGS. 1A and 1B andFIG. 2A correspond to the setting operation. In addition, an operationfor inputting the input voltage V_(in) and the bias voltage V_(b) andtaking out the output voltage V_(out) is referred to as an outputoperation. In this embodiment, the operation of FIG. 2B corresponds tothe output operation.

As described above, in the present invention, even if threshold voltagesfluctuate among transistors, in a transistor to which a signal voltagesuch as the input voltage V_(in) or the bias voltage V_(b) is inputted,a value found by adding a threshold value of the transistor and thesignal voltage is always inputted. Thus, an electric circuit in which aninfluence of variation of threshold voltages among transistors issuppressed can be provided.

(Embodiment 2)

In the source follower circuit shown in FIGS. 1 and 2, the case in whichit includes the n-channel type transistor for amplification 211 and then-channel type transistor for bias 212 is shown. Next, in thisembodiment, a source follower circuit including a p-channel typetransistor for amplification 211 and a p-channel type transistor forbias 212 is shown in FIGS. 7A to 7C, and its structure will bedescribed. Note that, since operations of the source follower circuitshown in FIGS. 7A to 7C follow the operations of the embodiment 1, adescription of the operations will be omitted here.

In FIGS. 7A to 7C, reference numeral 231 denotes a p-channel typetransistor for bias and 232 denotes a p-channel type transistor foramplification. Reference numerals 233 and 234 denote capacitancedevices. In addition, reference numerals 235 to 242 denote elementshaving a switching function, and preferably, a semiconductor elementsuch as a transistor or an analog switch is used. Reference numerals 243and 244 denote power supply lines, and a power supply voltage V_(dd) isapplied to the power supply line 243 and a ground voltage V_(ss) isapplied to the power supply line 244.

Note that, although the case in which the transistor for amplification232 and the transistor for bias 231 are the p-channel type is indicatedin this embodiment, polarities of both the transistors may be differentas in a push-pull circuit.

A source region of the transistor for bias 231 is connected to the powersupply line 243 and a drain region thereof is connected to the switches235 and 239. A gate electrode of the switch 236 and the capacitancedevice 233. Further, one terminal of the switch 238 is an outputterminal, and a voltage of the source region of the transistor foramplification 232 becomes the output voltage V_(out).

Note that sizes of the gate widths (W) and the gate lengths (L) of thetransistor for bias 231 and the transistor for amplification 232 are notspecifically limited.

In addition, in FIG. 7B, a source follower circuit in the case in whichthe transistor for bias 231 is not arranged is shown. Since operationsof the source follower circuit shown in FIG. 7B follow the operations ofFIGS. 1 and 2 described above except that the switch is turned OFF atthe time of the output operation, a description of the operations willbe omitted in this embodiment.

It is possible to arbitrarily combine this embodiment with theembodiment 1.

(Embodiment 3)

In the above-mentions embodiments 1 and 2, the source follower circuitto which the present invention is applied is described. However, thepresent invention can be applied to various circuits such as anarithmetic and logic unit represented by a differential amplifiercircuit, a sense amplifier, an operational amplifier, and the like. Inthis embodiment, an arithmetic and logic unit to which the presentinvention is applied will be described using FIGS. 8 to 10.

First, a differential amplifier circuit to which the present inventionis applied will be described using FIG. 8. In the differential amplifiercircuit, arithmetic operation of a difference between an input voltageV_(in1) and an input voltage V_(in2) is performed to output an outputvoltage V_(out).

In the differential amplifier shown in FIG. 8, reference numerals 272and 273 denote p-channel type transistors and 274, 275, and 286 denoten-channel type transistors. Reference numerals 276, 277, and 287 denotecapacitance devices. In addition, switches 278 to 285, a switch 351,switches 288 to 290 are elements having a switching function, andpreferably, a semiconductor element such as a transistor is used.Further, a power supply voltage V_(dd) is applied to a power supply line271 and a ground voltage V_(ss) is applied to a power supply line 291.

In the differential amplifier circuit shown in FIG. 8, a gate electrodeof the transistor 274 is an input terminal, and the input voltageV_(in1) is inputted to the gate electrode of the transistor transistorfor bias 231 is connected to one terminal of the capacitance device 233.The other terminal of the capacitance device 233 is connected to thepower supply line 243 via the switch 237. The capacitance device 233carries out a function of holding a voltage between the gate and thesource (threshold voltage) of the transistor for bias 231.

A drain region of the transistor for amplification 232 is connected tothe power supply line 244 and a source region thereof is connected tothe switches, 238, 239, and 242. A gate electrode of the transistor foramplification 232 is connected to one terminal of the capacitance device234. The other terminal of the capacitance device 234 is connected tothe source region of the transistor for amplification 232 via the switch242. The capacitance device 234 carries out a function of holding avoltage between the gate and the source (threshold voltage) of thetransistor for amplification 232.

Conduction or non-conduction (ON or OFF) of the switches 235 to 242 iscontrolled according to a signal to be inputted. However, in FIGS. 7A to7C, illustration of a signal line or the like for inputting a signal tothe switches 235 to 242 will be omitted in order to simplifyexplanation.

Note that, although the switch 238 is connected to the source region ofthe transistor for amplification 232 and connected to the drain regionof the transistor for bias 231 via the switch 239, the present inventionis not limited to this. The switch 238 may be connected to the drainregion of the transistor for bias 231 and connected to the source regionof the transistor for amplification 232 via the switch 239.

However, the switch 238 is preferably connected to the source region ofthe transistor for amplification 232 and connected to the drain regionof the transistor for bias 231 via the switch 239. This is because, inthe case in which the switch 238 is connected to the drain region of thetransistor for bias 231 and connected to the source region of thetransistor for amplification 232 via the switch 239, if there is an ONresistance in the switch 239, the output voltage V_(out) is affectedthereby and decreases.

In the source follower circuit shown in FIGS. 7A to 7C, one terminal ofthe switch 241 becomes an input terminal. An input voltage V_(in)(signal voltage) inputted form the input terminal is inputted to thegate electrode of the transistor for amplification 232 via the switch241 and the capacitance device 234. In addition, a bias voltage V_(b) isinputted from one terminal of the switch 236. The bias voltage V_(b) isinputted to the gate electrode of the transistor 231 via the 274. Inaddition, a gate electrode of the transistor 275 is also an inputterminal, and the input voltage V_(in2) is inputted to the gateelectrode of the transistor 275. Further, a drain region of thetransistor 275 is an output terminal, and a voltage of the drain regionof the transistor 275 becomes the output voltage V_(out).

A drain region of the transistor 272 is connected to the power supplyline 271 and a source region thereof is connected to a drain region ofthe transistor 274. A drain region of the transistor 273 is connected tothe power supply line 271 and a source region thereof is connected tothe drain region of the transistor 275. A gate electrode of thetransistor 272 and a gate electrode of the transistor 273 are connected.Note that resistors may be arranged instead of the transistors 272 and273.

The drain region of the transistor 274 is connected to the power supplyline 271 via the transistor 272 and a source region thereof is connectedto one terminal of the capacitance device 276 via the switch 282. Thegate electrode of the transistor 274 is connected to the other terminalof the capacitance device 276. The capacitance device 276 carries out afunction of holding a voltage between the gate and the source (thresholdvoltage) of the transistor 274.

The drain region of the transistor 275 is connected to the power supplyline 271 via the transistor 273 and a source region thereof is connectedto one terminal of the capacitance device 277 via the switch 283. Thegate electrode of the transistor 275 is connected to the other terminalof the capacitance device 277. The capacitance device 277 carries out afunction of holding a voltage between the gate and the source (thresholdvoltage) of the transistor 275.

A drain region of the transistor 286 is connected to the source regionof the transistor 274 and the source region of the transistor 275 viathe switch 285 and the switch 351, and a source region of the transistor286 is connected to one terminal of the capacitance device 287 via theswitch 290. A gate electrode of the transistor 286 is connected to theother terminal of the capacitance device 287. The capacitance device 287carries out a function of holding a voltage between the gate and thesource (threshold voltage) of the transistor 286.

Further, since descriptions of an operation for holding predeterminedelectric charges in the capacitance device 276, an operation for holdingpredetermined electric charges in the capacitance device 277, and anoperation for holding predetermined electric charges in the capacitancedevice 287 follow the embodiment 1, the operations will be describedbriefly.

First, as shown in FIG. 18, initialization is performed. In order toperform the initialization, it is sufficient to bring the transistors274, 275, and 286 into a state in which the transistors are turned ON.Then, as shown in FIG. 19, the transistors 274, 275, and 286 areoperated such that voltage between the gate and the sources of thetransistors converge on a threshold voltage.

Then, when holding of the predetermined electric charges in thecapacitance device 276 ends, as shown in FIG. 22, an input voltageV_(in1) is inputted to the gate electrode of the transistor 274, andwhen holding of the predetermined electric charges in the capacitancedevice 277 ends, an input voltage V_(in2) is inputted to the gateelectrode of the transistor 275. In addition, when holding of thepredetermined electric charges in the capacitance device 287 ends, abias voltage V_(b) is inputted to the gate electrode of the transistor286, and an output operation is performed. Since a description of theoperation at this point follow the embodiment 1, the description will beomitted in this embodiment.

Note that the circuit of FIG. 8 may be improved to be a circuit shown inFIG. 17. In FIG. 17, switches 352 and 353 are additionally arranged inparallel with the transistors 272 and 273. The switches 352 and 353 areturned ON when the setting operation is performed (at the time when athreshold voltage is being obtained) and are turned OFF at the time whenthe output operation is performed (at the time when the circuit isoperated as an ordinary differential circuit). By the addition of theswitches, an electric current can be easily supplied to the transistors274 and 275 at the time when the setting operation is performed, orvoltages of the drains of the transistors 274 and 275 can be easilyfixed.

In addition, in the circuits of FIGS. 8 and 17, positions of theswitches 285 and 351 are different. However, since it is sufficient tobring the transistors 274, 275, and 286 into a state in which thetransistors are not electrically connected at the time of an operationfor obtaining a threshold voltage, if this condition is satisfied, theswitches 285 and 351 may be arranged anywhere.

Subsequently, the case in which the transistors constituting thedifferential amplifier circuit shown in FIG. 8 has an oppositeconduction type will be described using FIGS. 9 and 23.

In differential amplifier circuits shown in FIGS. 9 and 23, referencenumeral 272 and 273 denotes n-channel type transistors and 274, 275, and286 are p-channel type transistors. The gate electrode of the transistor274 is an input terminal, and the input voltage V_(in1) is inputted tothe gate electrode of the transistor 274. In addition, the gateelectrode of the transistor 275 is also an input terminal, and the inputvoltage V_(in2) is inputted to the gate electrode of the transistor 275.Further, a voltage of the source region of the transistor 275 becomesthe output voltage V_(out). Moreover, the bias voltage V_(b) is inputtedto the gate electrode of the transistor 286.

Note that, in the differential amplifier circuits shown in FIGS. 9 and23, structures and operations are the same as those of the differentialamplifier circuits shown in FIGS. 8 and 17 except that the power supplyvoltage V_(dd) is applied to the power supply line 291 and the groundvoltage V_(ss) is applied to the power supply line 271, a descriptionthereof will be omitted here.

In addition, although the electric circuits shown in FIGS. 8 and 9 areshown as differential amplifier circuits in this embodiment, the presentinvention is not limited to this, and the electric circuits can be alsoused as other arithmetic and logic units such as a sense amplifier byappropriately changing voltages inputted as the input voltage V_(in1)and the input voltage V_(in2).

Next, an operational amplifier to which the present invention is appliedwill be described using FIGS. 10A and 10B. FIG. 10A shows circuitsymbols of the operational amplifier and FIG. 10B shows a circuitstructure of the operational amplifier.

Note that there are various structures as the circuit structure of theoperational amplifier. Therefore, in FIGS. 10A and 10B, the case inwhich a source follower circuit is combined with a differentialamplifier circuit is described as the simplest case. Thus, the circuitstructure is not limited to FIGS. 10A and 10B.

In the operational amplifier shown in FIG. 10A, characteristics aredefined by a relationship between the input voltages V_(in1) and V_(in2)and the output voltage V_(out). More specifically, the operationalamplifier has a function of outputting the output voltage V_(out) bymultiplying a voltage of a difference between the input voltage V_(in1)and the input voltage V_(in2) by a degree of amplification A.

In the operational amplifier shown in FIG. 10B, the gate electrode ofthe transistor 274 is an input terminal, and the input voltage V_(in1)is inputted to the gate electrode of the transistor 274. In addition,the gate electrode of the transistor 275 is also an input terminal, andthe input voltage V_(in2) is inputted to the gate electrode of thetransistor 275. In addition, a voltage of the source region of thetransistor 292 becomes the output voltage V_(out). Further, a biasvoltage is inputted to the gate electrode of the transistor 286.

In the circuit shown in FIG. 10B, a portion enclosed by a dotted linedenoted by reference numeral 305 has the same structure as thedifferential amplifier circuit shown in FIG. 8. Further, since a portionenclosed by a dotted line denoted by reference numeral 306 is the sameas the source follower circuit shown in FIGS. 1 and 2, a description ofa detailed structure of the operational amplifier shown in FIG. 10B willbe omitted.

In addition, an operational amplifier in the case in which a transistor299 is the p-channel type is shown in FIGS. 21A and 21B. In FIG. 21B,one terminal of a capacitance device 300 is connected to the drainregion of the transistor 275 via the switches 302 and 278.

Note that it is possible to arbitrarily combine this embodiment with theembodiments 1 and 2.

(Embodiment 4)

This embodiment explains a pixel and a driving circuit (a bias circuit)of the configuration and operation in a semiconductor device having aphotoelectric device to which the invention is applied, by using FIGS.11 and 12.

The semiconductor device shown in FIG. 11A has a pixel region 702 havinga plurality of pixels arranged in a matrix form on a substrate 701.Around the pixel region 702, there are provided a signal-line drivecircuit 703 and first to fourth scanning line drive circuits 704 to 707.Although the semiconductor device of FIG. 11A has the signal line drivecircuit 703 and the first to fourth scanning line drive circuits 704 to707, the invention is not limited to this, i.e. the signal line drivecircuit and scanning line drive circuits are arbitrarily arranged in thenumber depending upon a pixel configuration. Also, signals areexternally supplied to the signal line drive circuit 703 and first tofourth scanning line drive circuits 704 to 707 through an FPC 708.However, the invention is not limited to this but the electric circuitsother than the pixel region may be use an IC to externally supplysignals.

First explained is a configuration of the first scanning line drivecircuit 704 and second scanning line drive circuit 705, by using FIG.11B. The third scanning line drive circuit 706 and the fourth scanningline drive circuit 707 conform to the diagram of FIG. 11B, and hencegraphic display is omitted.

The first scanning line drive circuit 704 has a shift register 709 and abuffer 710. The second scanning line drive circuit 705 has a shiftregister 711 and a buffer 712. Briefly explain the operation, the shiftregister 709, 711 sequentially outputs sampling pulses according to aclock signal (G-CLK), start pulse (S-SP) and clock inversion signal(G-CLKb). Thereafter, the pulse amplified by the buffer 710, 712 isinputted to scanning lines and made in a selective state row by row.

Note that configuration may be made such that a level shifter isarranged between the shift register (709, 711) and the buffer (710,712). The arrangement of a level shifter circuit can increase voltageamplitude.

Next explained is the configuration of the signal line drive circuit703, by using FIG. 11C.

The signal line drive circuit 703 has a signal output line drive circuit715, a sample hold circuit 716, a bias circuit 714 and an amplifiercircuit 717. If functions of each circuits are easily explained, thebias circuit 714, in a pair with an amplifier transistor of each pixel,forms a source follower circuit. The sample hold circuit 716 has afunction to temporarily store a signal, make an analog-digitalconversion and reduce noise. The signal output line drive circuit 715has a signal output function to sequentially output temporarily storedsignals. The amplifier circuit 717 has a circuit to amplify a signaloutputted from the sample hold circuit 716 and signal output line drivecircuit 715. Incidentally, the amplifier circuit 717 may not be arrangedwhere no signal amplification is required.

Explanation is made on the configuration and operation of a circuit of apixel 713 arranged at i-th column and j-th row in the pixel region 702and a bias circuit 714 at around the i-th column, by using FIG. 12.

First explained is the configuration of the circuit of the pixel 713arranged at i-th column and j-th row and the bias circuit 714 at aroundthe i-th column.

The pixel of FIG. 12 has first to fourth scanning lines Ga(j) to Gd(j),a signal line S(i) and a power line V(i), and also an n-channeltransistor 255, a photoelectric converter device 257 and switches 250 to254.

Although the transistor 255 is the n-channel type in this embodiment,the invention is not limited to this, i.e. it may be a p-channel type.However, because the transistor 255 and the transistor 260 form a sourcefollower circuit, the both transistors are preferably in the samepolarity.

The switches 250 to 254 are semiconductor devices having switchingfunctions, which preferably use transistors. The switches 251 and 252are on-off controlled according to a signal inputted through the firstscanning line Ga(j). The switch 250 is on-off controlled according to asignal inputted through the second scanning line Gb(j). The switch 253is on-off controlled according to a signal inputted through the thirdscanning line Gc(j). The switch 254 is on-off controlled according to asignal inputted through the fourth scanning line Gd(j).

The transistor 255 has source and drain regions one of which isconnected to a power line V(i) and the other is connected to a signalline S(i) through the switch 250. The transistor 255 has a gateelectrode connected to one terminal of a capacitance device 256. Theother terminal of the capacitance device 256 is connected to oneterminal of a photoelectric converter device 257 through the switch 253.The other terminal of the photoelectric converter device 257 isconnected to a power line 258. The power line 258 is applied with aground potential V_(ss). The capacitance device 256 has a role to hold avoltage between the gate and the source (a threshold voltage) of thetransistor 255.

The bias circuit 714 has a transistor 260, a capacitance device 261 andswitches 259, 262 and 263. The transistor 260 has a source regionconnected to a power line 264 and a drain region connected to the signalline S(i). The power line 264 is applied with a ground potential V_(ss).The transistor 260 has a gate electrode connected to one terminal of thecapacitance device 261. The other terminal of the capacitance device 261is connected to the power line 264 via a switch 262. The capacitancedevice 261 has a role to hold a voltage between the gate and the source(a threshold voltage) of the transistor 260.

In FIG. 12, the region surrounded by the dotted line shown at 719 andregion surrounded by the dotted line shown at 714 corresponds to asource follower circuit.

Next explained briefly is the operation of the circuit of the pixel 713arranged at i-th column and j-th row and the bias circuit 714 at aroundthe i-th column.

At first, the switches 250 to 252 of the pixel 713 and the switches 259and 262 of the bias circuit 714 are turned into an on-state. The otherswitches than those are turned off. Thereupon, a potential difference iscaused between the power source line V(i) and the power source line 264.As a result, a current flows toward the power source line 264 from thepower source line V(i) via switches 252 and 251, then, via switches 250and 259, and then, via the switch 262.

In the instant a current begins to flow, no charge is held on thecapacitance devices 256, 261. Consequently, the transistors 255, 260 areoff.

Then, charge is gradually built up on the capacitance devices 256 and261 to cause a potential difference between the both electrodes of thecapacitance devices 256, 261. When the potential difference between theboth electrodes of the capacitance devices 256 and 261 reaches athreshold voltage of the transistors 255, 260, the transistors 255 and260 turn on.

Then, charges continue to accumulate in the capacitance devices 256 and261 until they become a steady state.

After the capacitance devices 256 and 261 complete the charge storageinto a steady state, the switch 250 is turned off. The switches 251, 252are kept on. The switches 259, 262 are also kept on. The other switchesthan the above are all off.

Then, positive electric charges held in the capacitance device 256 flowin the direction of the capacitance device 256 via the switch 252, thetransistor 255 and the switch 251. More specifically, the positiveelectric charges held in the capacitance device 256 flow in thedirection of the capacitance device 256 via the switch 252, the sourceregion of the transistor 255, the drain region thereof, and the switch251. As a result, the potential difference between both the electrodesof the capacitance device 256 are decreasing. This operation isperformed until the transistor 255 is turned off. That is, the operationis continued until the electric charges held in the capacitance element256 become the same value as the threshold voltage of the transistor255.

In addition, positive electric charges held in the capacitance device261 flow in the direction of the power supply line 264 via the switch259, the transistor 260. More specifically, positive electric chargesheld in the capacitance device 261 flow to the power supply line 264 viaa switch 259, the source region of the transistor 260 and the drainregion thereof. This operation is performed until the transistor 260 isturned OFF. That is, the operation is continued until the electriccharges held in the capacitance device 261 become the same value as thethreshold voltage of the transistor 260.

At this time, the threshold voltage of the transistor 255 is held in thecapacitance device 256 and the threshold voltage of the transistor 260is held in the capacitance device 261. Subsequently, in this state, theswitches 250, 253 in the pixel 713 are turned on while the otherswitches than those are turned off. The switch 263 in the bias circuit714 is turned on while the other switches than those are turned off.

Thereupon, the gate electrode of the transistor 255 is inputted by asignal from the photoelectric converter device 257 through thecapacitance device 256. At the same time, the gate electrode of thetransistor 260 is inputted by a bias potential V_(b) from through thecapacitance device 261.

At this time, the gate electrode of the transistor 255 is inputted by avalue having the signal of from the photoelectric converter device 257added onto the threshold voltage held on the transistor. The gateelectrode of the transistor 260 is inputted by a value having the biaspotential added onto the threshold voltage held on the transistor.Namely, the signals to be inputted to the gate electrode of thetransistors 255 and 260 are signals to be inputted to gate electrodes ofthe transistor in addition to the threshold voltage held on transistors255 and 260. Consequently, it is possible to suppress against theaffection of transistor characteristic variation.

Then, the potential on the source region of the transistor 255 becomesan output potential V_(out). The output potential V_(out) is outputted,as a signal having been read by the photoelectric converter device 257,onto the signal line S(i) via the switch 250.

Next, the switch 254 is turned on while the other switches than thoseare turned off, to initialize the photoelectric converter device 257.More specifically, the charge held by the photoelectric converter device257 is allowed to flow toward the power line V(i) through the switch 254such that the potential on an n-channel terminal of the photoelectricconverter device 257 becomes equal to the potential on the power line258. From then on, the above operation is repeated.

The semiconductor device having the above configuration can suppressagainst the affection of a transistor threshold voltage variation.

The invention can be desirably combined with Embodiments 1-3.

(Embodiment 5)

This embodiment explains an example, different from Embodiments 2 to 4,of an electric circuit to which the invention is applied, by using FIGS.13 to 16.

In FIG. 13A, 310 is the source follower circuit of FIGS. 1 and 2. Sincethe circuit configuration and operation of the source follower circuit310 is similar to that of FIGS. 1 and 2, description is omitted in thisembodiment.

The operation of the source follower circuit 310 is to be roughlydivided with setting and output operations, as mentioned before.Incidentally, setting operation is an operation to hold predeterminedcharge on a capacitance element, which corresponds to the operation inFIGS. 1A, B and 2A. Meanwhile, output operation is an operation to inputan input voltage V_(in) and a bias potential V_(b) to take out an outputpotential V_(out), which corresponds to the operation in FIG. 2B.

In the source follower circuit 310, a terminal a corresponds to theinput terminal while a terminal b corresponds to the output terminal.The switches 216, 218, and 221 are controlled by a signal inputtedthrough a terminal c. The switches 215, 217, 220 and 222 are controlledaccording to a signal inputted through a terminal d. The switch 129 iscontrolled according to a signal inputted through a terminal e.

In designing an electric circuit having a source follower circuit 310,it is preferred to arrange at least two source follower circuits 315 and316 as shown in FIG. 13B. One of the source follower circuits 315 and316 is preferably to carry out a setting operation while the other is tocarry out an output operation. Because this can carry out two operationsat the same time, there is no uselessness in operation requiring uselesstime. Thus, electric circuit operation can be effected at high speed.

For example, in a design using a source follower circuit to asignal-line drive circuit, at least two source follower circuits arepreferably arranged on each signal lines. In a design using a sourcefollower circuit to a scanning-line drive circuit, at least two sourcefollower circuits are preferably arranged on each scanning lines. In adesign using a source follower circuit on the pixel, at least two sourcefollower circuits are preferably arranged on each pixel.

In FIG. 13B, 311 to 314 are devices having switch functions, preferablytransistors are used. When the switches 311 and 312 are on, the switches313 and 314 are off. When the switches 311 and 312 are off, the switches313 and 314 are on. In this manner, of the two source follower circuits315 and 316, one is cause to carry out a setting operation while theother is caused to carry out an output operation. Incidentally, the twosource follower circuits 315 and 316 may be controlled by controllingthe switches 216 and 218 possessed by the source follower circuit 310without arranging the switches 311 to 314.

Although, in this embodiment, the region surrounded by the dotted line315, 316 was assumed corresponding to the source follower circuit, theinvention is not limited to this, i.e. the differential amplifiercircuit, operational amplifier or the like shown in FIGS. 7 to 10 or thelike may be applied.

This embodiment explains the configuration and operation of asignal-line drive circuit having at least two source follower circuitsarranged based on each signal lines, by using FIGS. 14 to 16.

FIG. 14 shows a signal-line drive circuit. The signal-line drive circuithas a sift register 321, a first latch circuit 322, a second latchcircuit 323, a D/A converter circuit 324 and a signal amplifier circuit325.

Note that, in the case that the first latch circuit 322 or second latchcircuit 323 is a circuit capable of storing analog data, the D/Aconverter circuit 324 in many cases is to be omitted. In the case thatthe data to be outputted onto the signal line is binary, i.e. digitalamount, the D/A converter circuit 324 in many cases is to be omitted.Meanwhile, the D/A converter circuit 324, in a certain case,incorporates therein a gamma-correction circuit. In this manner, thesignal-line drive circuit is not limited to the configuration of FIG.17.

Briefly explaining the operation, the shift register 321 is configuredusing a plurality of columns of flip-flop circuits (FFs) or the like, toinput an input clock signal (S-CLK), a start pulse (SP) and a clockinversion signal (S-CLKb). Sampling pulses are to be sequentiallyoutputted according to the timing of these signals.

The sampling pulse outputted from the shift register 321 is inputted tothe first latch circuit 322. The first latch circuit 322 is inputtedwith a video signal, to hold the video signal on each column accordingto the input timing of the sampling pulse.

In the first latch circuit 322, when video-signal holding is completedto the last column, a latch pulse is inputted to the second latchcircuit 323 during a horizontal retrace period. Thus, the video signalsheld on the first latch circuit 322 are transferred, at one time, to thesecond latch circuit 323. Thereafter, the video signals held on thesecond latch circuit 323 are inputted, simultaneously in an amount ofone row, to the D/A converter circuit 324. The signal to be inputtedfrom the D/A converter circuit 324 is inputted to the signal amplifiercircuit 325.

While the video signal held on the second latch circuit 323 is beinginputted to the D/A converter circuit 324, the shift register 321 againoutputs a sampling pulse. From then on, the operation is repeated.

Explanation is made on the configuration of the signal amplifier circuit325 at around i-th column to (i+2)-th column, or three, signal lines, byusing FIG. 15.

The signal amplifier circuit 325 has two source follower circuits 315and 316 on each column. Each of the source follower circuits 315 and 316has five terminals, i.e. terminal a to terminal e. The terminal acorresponds to an input terminal of the source follower circuit 315 and316 while the terminal b corresponds to an output terminal of the sourcefollower circuit 315 and 316. Meanwhile, the switches 216, 218 and 221are controlled according to a signal inputted through the terminal cwhile the switches 215, 217, 220 and 222 are controlled according to asignal inputted through the d. Furthermore, the switch 219 is controlledaccording to a signal inputted through the terminal e.

In the signal amplifier circuit 325 shown in FIG. 15, a logic operatoris arranged between the three signal lines, i.e. signal line forinitialization 326, a setting signal line 327 and a threshold signalline 328 and the source follower circuit 315 and 316. 329 is aninverter, 330 is an AND, 331 is an OR, 332 is an inverter, 333 is anAND, 334 is an inverter and 335 is an OR. Inputted, to the terminal c toterminal e, is either a signal outputted from the setting signal line327 or a signal outputted from an output terminal of the above-mentionedlogic operators.

Next explained are the signals to be outputted from the three signallines, i.e. the signal line for initialization 326, the setting signalline 327 and the threshold signal line 328, and the signals to beinputted to the switches through the terminal c to terminal e of thesource follower circuit 315 by using FIG. 16.

Note that the switch the signal is to be inputted through the terminal cto terminal e is turned on when a High signal is inputted and off when aLow signal is inputted.

The signals as shown in FIG. 16 are inputted through the three signallines, i.e. the signal line for initialization 326, the setting signalline 327 and the threshold signal line 328. Furthermore, a signaloutputted from the setting signal line 327 is inputted, as it is, to theterminal c of the source follower circuit 315. A signal outputted froman output terminal of the AND 333 is inputted to the terminal d while asignal outputted from an output terminal of the OR 331 is inputted tothe terminal e. By doing so, the source follower circuit 315 can becontrolled for any one of setting and outputting operations.

Also, a signal outputted from an output terminal of the inverter 332 isinputted to the terminal c of the source follower circuit 316. A signaloutputted from an output terminal of the AND 330 is inputted to theterminal d while a signal outputted from the OR is inputted, as it is,to the terminal e. By doing so, the source follower circuit 316 can becontrolled for any one of setting and outputting operations.

Incidentally, the signal line drive circuit, in many cases, has aplurality of pixels connected at the end of each signal line thereof.The pixel, in many cases, is to change its state depending upon avoltage inputted through the signal line. This may be a pixel having aliquid crystal device or a light emitting device typified by an organicEL, for example. Besides these, connection is possible with a device ofvarious configurations.

This embodiment can be desirably combined with Embodiments 1 to 4.

(Embodiment 6)

The electronic apparatus using the electric circuit of the inventionincludes a video camera, a digital camera, a goggle-type display(head-mount display), a navigation system, an audio reproducingapparatus (car audio unit, audio components, etc.), a laptop, a gameapparatus, a personal digital assistant (mobile computer, cellularphone, portable game machine or electronic book, etc.), an imagereproducing apparatus having a recording medium (specifically, apparatusfor reproducing a recording medium such as a Digital Versatile Disk(DVD) etc. and having a display to display an image thereof) and thelike. FIGS. 20A to 20H show detailed examples of these electronicapparatus.

FIG. 20A is a display (light emitting apparatus) including a housing3001, a support base 3002, a display part 3003, a speaker part 3004, avideo-input terminal 3005 and the like. The present invention can beused in an electric circuit configuring the display part 3003. Also, thelight emitting apparatus of FIG. 20A can be completed by the invention.Because the light emitting apparatus is of a spontaneous emission type,a backlight is not required. Thus, the display part can be made smallerin thickness than the liquid crystal display. Incidentally, the lightemitting apparatus includes a display unit for displaying all the piecesof information for personal computers, TV broadcast reception,displaying advertisement and so on.

FIG. 20B is a digital still camera, including a main body 3101, adisplay part 3102, an image receiving part 3103, operation keys 3104, anexternal connection port 3105, a shutter 3106 and the like. Theinvention can be used in an electric circuit configuring the displaypart 3102. Also, the digital still camera of FIG. 20B is to be completedby the invention.

FIG. 20C is a laptop, including a main body 3201, a housing 3202, adisplay part 3203, a keyboard 3204, an external connection port 3205, apointing mouse 3206 and the like. The invention can be used in anelectric circuit configuring the display part 3203. Also, the lightemitting device of FIG. 20C is to be completed by the invention.

FIG. 20D is a mobile computer, including a main body 3301, a displaypart 3302, a switch 3303, operation keys 3304, an infrared ray port 3305and the like. The invention can be used in an electric circuitconfiguring the display part 3302. Also, the mobile computer of FIG. 20Dis completed by the invention.

FIG. 20E is a portable image reproducing apparatus having a recordingmedium (specifically, DVD reproducing apparatus), including a main body3401, a housing 3402, a display part-A 3403, a display part-B 3404, arecording-medium (DVD or the like) reading part 3405, operation keys3406, a speaker part 3407 and the like. The display part-A 3403 is todisplay, mainly, image information while the display part-B 3404 is todisplay, mainly, character information. The invention can be used in anelectric circuit configuring the display parts A, B 3403, 3404.Incidentally, the image reproducing apparatus having a recording mediumincludes a home-use game apparatus and the like. Also, the DVDreproducing apparatus of FIG. 20E is to be completed by the invention.

FIG. 20F is a goggle-type display (head-mount display), including a mainbody 3501, a display part 3502 and an arm part 3503. The invention canbe used in an electric circuit configuring the display part 3502. Also,the goggle-type display of FIG. 20F is to be completed by the invention.

FIG. 20G is a video camera, including a main body 3601, a display part3602, a housing 3603, an external-connection port 3604, a remote-controlreceiving part 3605, an image receiving part 3606, a battery 3607, asound input part 3608, operation keys 3609 and the like. The inventioncan be used in an electric circuit configuring the display part 3602.Also, the video camera of FIG. 20G is to be completed by the invention.

FIG. 20H is a cellular phone, including a main body 3701, a housing3702, a display part 3703, a sound input part 3704, a sound output part3705, operation keys 3706, an external-connection port 3707, an antenna3708 and the like. The invention can be used in an electric circuitconfiguring the display part 3703. Incidentally, the display part 3703can suppress the cellular phone from consuming current by displayingwhite characters on a black background. Also, the cellular phone of FIG.20H is to be completed by the invention.

Incidentally, if light emitting material will increase light emissionbrightness in the future, the light containing output image informationcan be used, by magnifying and projecting by a lens or the like, on afront or rear type projector.

Meanwhile, concerning the above electronic apparatuses, there areincreasing cases to display the information distributed through anelectronic communication line, such as the Internet or CATV (cabletelevision). Particularly, there are increased occasions to displaymoving-image information. Because light emitting material has a veryhigh response speed, the light emitting device is preferred fordisplaying moving-images.

Meanwhile, it is desired for the light emitting device to displayinformation such that a light emitting area is reduced to a possibleless extent because the light emitting area consumes power. Accordingly,in the case of using a light emitting device in a display part, mainlyfor character information, of a personal digital assistant such asparticularly a cellular phone or audio reproducing apparatus, it isdesired to carry out driving such that character information is formedby a light emitting part with non-emitting part provided as abackground.

As described above, the present invention, having an extremely broadscope of application, can be used on an electronic apparatus in everyfield. Also, the electronic apparatus of the embodiment may use anyconfiguration of the electric circuits and semiconductor devices shownin Embodiments 1 to 5.

The present invention which realizes the effect of controlling theaffection of a characteristic variation of TFT greatly contributes tothe technology which forms a pixel and a driving circuit on the samesubstrate by using polycrystal semiconductor (polysilicon). And anespecially excellent effect is brought to the personal digitalassignment among the above-mentioned electronics.

Advantage of the Invention

The present invention provides an electric circuit which is arrangedsuch that both electrodes of a capacitance device can hold a voltagebetween the gate and the source of a specific transistor. Further, thepresent invention provides an electric circuit which has a functioncapable of setting a potential difference between both electrodes of acapacitance device so as to be a threshold voltage of a specifictransistor.

Moreover, in the present invention, a voltage between the gate and thesource of a specific transistor held in a capacitance device ispreserved as it is, and a signal voltage (voltage of a video signal,etc.) is inputted to a gate electrode of the transistor. Then, a voltagewith the signal voltage added to the voltage between the gate and thesource preserved in the capacitance device is inputted to the gateelectrode of the transistor. As a result, a value found by adding athreshold voltage of the transistor and the signal voltage is inputtedto the gate electrode of the transistor. That is, in the presentinvention, even if threshold voltages fluctuate among transistors, thevalue found by adding the threshold value of the transistor and thesignal voltage is always inputted to a transistor to which a signalvoltage is inputted. Thus, an electric circuit can be provided in whichan influence of the variation of threshold values among transistors issuppressed.

Accordingly, other embodiments are within the scope of the followingclaims.

1. An electric circuit for outputting an output voltage to an output terminal based on an input voltage to be inputted from an input terminal, the electric circuit comprising: a transistor; a capacitance device connected between a gate electrode and a source electrode of said transistor, said capacitance device comprising first and second electrodes; a first switch operable to make a potential of one of the first and second electrodes of the capacitance device correspond to a power supply voltage; a second switch operable to make a potential difference between the first and second electrodes of the capacitance device correspond to a threshold voltage of said transistor; and a third switch for outputting said output voltage to said output terminal from said source electrode of said transistor when said input voltage is inputted to the other one of the first and second electrode of the capacitance device, wherein the first switch is connected between the gate electrode and the drain electrode of the transistor and switches a connection and a disconnection between the gate electrode and the drain electrode of the transistor.
 2. An electric circuit for outputting an output voltage based on an input voltage to be inputted from an input terminal, the electric circuit comprising: a first transistor and a second transistor connected in series; a first capacitance device connected between a gate electrode and a source electrode of said first transistor; a second capacitance device connected between a gate electrode and a source electrode of said second transistor; a first switch for connecting the source electrode of the first transistor and a drain electrode of the second transistor; a second switch for making a potential difference between first and second electrodes of said first capacitance device into a threshold voltage of said first transistor; a third switch for making a potential difference between first and second electrodes of said second capacitance device into a threshold voltage of said second transistor; and a fourth switch for outputting said output voltage from said source electrode of said first transistor when said input voltage is input to one of the first and second electrodes of the first capacitance device and a bias voltage is input to one of the first and second electrodes of the second capacitance device.
 3. The electric circuit according to claim 1, wherein said first switch applies a threshold voltage of said transistor to a voltage between said gate electrode and said source electrode of said transistor.
 4. The electric circuit according to claim 1, wherein said voltage to be inputted in said gate electrode of said transistor is a value of a sum of said input voltage and said threshold voltage of said transistor.
 5. The electric circuit according to claim 2, wherein said first switch applies said threshold voltage of said first transistor to a voltage between said gate electrode and said source electrode of said first transistor, and said second switch applies said threshold voltage of said second transistor to a voltage between said gate electrode and said source electrode of said second transistor.
 6. The electric circuit according to claim 2, wherein said first voltage to be inputted in said gate electrode of said first transistor is a value of a sum of said input voltage and said threshold voltage of said first transistor, and said second voltage to be inputted in said gate electrode of said second transistor is a value of a sum of a bias voltage and said threshold voltage of said second transistor.
 7. The electric circuit according to claim 2, wherein said first transistor and said second transistor are of the same conduction type.
 8. The electric circuit according to claim 1, wherein said input voltage is a voltage of a signal to be supplied from a photoelectric conversion element.
 9. The electric circuit according to claim 1, wherein said electric circuit constitutes one selected from a source follower circuit, a differential amplifier, an operational amplifier, and an amplifier circuit.
 10. The electric circuit according to claim 2, wherein said input voltage is a voltage of a signal to be supplied from a photoelectric conversion element.
 11. The electric circuit according to claim 2, wherein said electric circuit constitutes one selected from a source follower circuit, a differential amplifier, an operational amplifier, and an amplifier circuit.
 12. An electric circuit comprising: first and second transistors; first, second, third, fourth, fifth, sixth and seventh switches; first and second capacitance devices; and first and second input terminals; wherein: a terminal of said first switch is electrically connected to a gate electrode of said first transistor and another terminal of said first switch is electrically connected to a drain electrode of said first transistor, an electrode of said first capacitance device is electrically connected to said gate electrode of said first transistor, and another electrode of said first capacitance device is electrically connected to said first input terminal via said second switch and a source electrode of said first transistor via said third switch, a terminal of said fourth switch is electrically connected to a gate electrode of said second transistor and another terminal of said fourth switch is electrically connected to a drain electrode of said second transistor, an electrode of said second capacitance device is electrically connected to said gate electrode of said second transistor, and another electrode of said second capacitance device is electrically connected to said second input terminal via said fifth switch and a source electrode of said second transistor via said sixth switch, and a terminal of said seventh switch is electrically connected to said source electrode of said first transistor and another terminal of said seventh switch is electrically connected to said drain electrode of said second transistor.
 13. The electric circuit according to claim 12, wherein said gate electrode of said first transistor is applied a voltage with a value of a sum of an input voltage input from said first input terminal and a threshold voltage of said first transistor when said second switch is ON.
 14. The electric circuit according to claim 12, wherein said gate electrode of said second transistor is applied a voltage with a value of a sum of a bias voltage input from said second input terminal and a threshold voltage of said second transistor when said fifth switch is ON.
 15. The electric circuit according to claim 12, wherein said first transistor and said second transistor are of the same conduction type.
 16. The electric circuit according to claim 12, wherein an input voltage input from said first input terminal is supplied from a photoelectric conversion element.
 17. The electric circuit according to claim 12 further comprising an eighth switch, wherein a terminal of said eighth switch is electrically connected to an output terminal, and another terminal of said eighth switch is electrically connected to one of said source electrode of said first transistor and said drain electrode of said second transistor.
 18. The electric circuit according to claim 17, wherein said output terminal is electrically connected to a pixel.
 19. The electric circuit according to claim 18, wherein said pixel includes one of a liquid crystal device and an organic EL device.
 20. The electric circuit according to claim 12, wherein said electric circuit constitutes an operational amplifier.
 21. The electric circuit according to claim 12, wherein said electric circuit constitutes one selected from the group consisting of a digital still camera, a laptop, a mobile computer, a portable image reproducing apparatus having a recording medium, a goggle-type display, a video camera and a cellular phone.
 22. An electric circuit comprising: first through third transistors; first through eleventh switches; and first through third capacitance devices; wherein: a terminal of said first switch is electrically connected to a gate electrode of said first transistor and another terminal of said first switch is electrically connected to a drain electrode of said first transistor, an electrode of said first capacitance device is electrically connected to said gate electrode of said first transistor, and another electrode of said first capacitance device is electrically connected to a first input terminal via said second switch and a source electrode of said first transistor via said third switch, a terminal of said fourth switch is electrically connected to a gate electrode of said second transistor and another terminal of said fourth switch is electrically connected to a drain electrode of said second transistor, an electrode of said second capacitance device is electrically connected to said gate electrode of said second transistor, and another electrode of said second capacitance device is electrically connected to a second input terminal via said fifth switch and a source electrode of said second transistor via said sixth switch, a terminal of said seventh switch is electrically connected to said source electrode of said first transistor and another terminal of said seventh switch is electrically connected to said drain electrode of said second transistor, a terminal of said eighth switch is electrically connected to a gate electrode of said third transistor and another terminal of said eighth switch is electrically connected to a drain electrode of said third transistor, an electrode of said third capacitance device is electrically connected to said gate electrode of said third transistor, and another electrode of said third capacitance device is electrically connected to a third input terminal via said ninth switch and a source electrode of said third transistor via said tenth switch, and a terminal of said eleventh switch is electrically connected to said source electrode of said third transistor, and another terminal of said eleventh switch is electrically connected to one of said source electrode of said first transistor and said drain electrode of said second transistor.
 23. The electric circuit according to claim 22, wherein said gate electrode of said first transistor is applied a voltage with a value of a sum of an input voltage input from said first input terminal and a threshold voltage of said first transistor when said second switch is ON.
 24. The electric circuit according to claim 22, wherein said gate electrode of said second transistor is applied a voltage with a value of a sum of a bias voltage input from said second input terminal and a threshold voltage of said second transistor when said fifth switch is ON.
 25. The electric circuit according to claim 22, wherein said gate electrode of said third transistor is applied a voltage with a value of a sum of an input voltage input from said third input terminal and a threshold voltage of said third transistor when said ninth switch is ON.
 26. The electric circuit according to claim 22, wherein said first transistor, said second transistor and said third transistor are of the same conduction type.
 27. The electric circuit according to claim 22 further comprising a twelfth switch, wherein a terminal of said twelfth switch is electrically connected to an output terminal, and another terminal of said twelfth switch is electrically connected to said drain electrode of said third transistor.
 28. The electric circuit according to claim 27, wherein said output terminal is electrically connected to a pixel.
 29. The electric circuit according to claim 28, wherein said pixel includes one of a liquid crystal device and an organic EL device.
 30. The electric circuit according to claim 22, wherein said electric circuit constitutes an operational amplifier.
 31. The electric circuit according to claim 22, wherein said electric circuit constitutes one selected from the group consisting of a digital still camera, a laptop, a mobile computer, a portable image reproducing apparatus having a recording medium, a goggle-type display, a video camera and a cellular phone.
 32. The electric circuit according to claim 22 further comprising a fourth transistor and a fifth transistor, wherein: a gate electrode of said fourth transistor is electrically connected to a drain electrode of said fourth transistor and a gate electrode of said fifth transistor; said drain electrode of said fourth transistor is electrically connected to said drain electrode of said first transistor; said drain electrode of said fifth transistor is electrically connected to said drain electrode of said third transistor; and a source electrode of said fourth transistor is electrically connected to a source electrode of said fifth transistor.
 33. The electric circuit according to claim 32 further comprising a thirteenth switch and a fourteenth switch, wherein: a terminal of said thirteenth switch is electrically connected to said drain electrode of said fourth transistor, and another terminal of said thirteenth switch is electrically connected to source electrode of said fourth transistor, and a terminal of said fourteenth switch is electrically connected to said drain electrode of said fifth transistor, and another terminal of said fourteenth switch is electrically connected to source electrode of said fifth transistor. 